Nonlinear dynamic behavior analysis of a DC/DC converter with an ultrahigh frequency Zsource converter
Shan Li^{1} , Sen Cui^{2} , Yan Chen^{3} , Yong Zheng^{4} , Wenxu Si^{5}
^{1, 2, 3, 5}School of Electrical and Electronic Engineering, Chongqing University of Technology, Chongqing, 400054, China
^{4}Engineering Research Center of Mechanical Testing Technology and Equipment, Ministry of Education, Chongqing, 400054, China
^{3}Corresponding author
Journal of Vibroengineering, Vol. 18, Issue 8, 2016, p. 55065520.
https://doi.org/10.21595/jve.2016.17620
Received 26 August 2016; received in revised form 1 November 2016; accepted 21 November 2016; published 31 December 2016
JVE Conferences
Zsource converters have been used in new energy sources because of their advantages. These converters have attracted considerable attention under highfrequency conditions given their high power density and high conversion efficiency. However, the stability of a system of ultrahigh frequency Zsource converters are likely to be affected because of the inappropriate selection of parameters or the interference of weak signals in the process of the system. These factors will render such converters unable to work properly. The chaotic bifurcation behavior of Zsource converters based on peak current control mode is analyzed in this study. A precise discrete iterative mapping model for such converters is established, and the regional stability of a system is determined based on the characteristic value of changes in the Jacobian matrix. Finally, the bifurcation and chaos phenomena in a highfrequency Zsource converter and the accuracy of the aforementioned analysis are verified via experiments. The conclusion drawn from this study does not only can provide a reference for the stable operation of ultrahigh frequency Zsource converters, but also presents a theoretical basis for optimizing system parameters and improving control performance.
Keywords: ultrahigh frequency Zsource converter, discrete iterative mapping, bifurcation, chaos, stability.
1. Introduction
A power converter is a strongly nonlinear control system. The opening and closing of cycles under different topologies are achieved by turning the switch tube on or off, which can easily cause the nonlinear behavior of switching converters. Period doubling bifurcation, boundary collision bifurcation and chaos, and other nonlinear phenomena [13] in DC/DC converters [4, 5], DC/AC inverters [6], and power factor correction converters [7] are common nonlinear behavior. When a power converter works in a chaotic region, the stable running state of a system will be changed, and its control performance will be considerably affected. The ripple of the voltage will enlarge, which is a serious situation, and the converter will be unable to work properly.
At present, research on the field of power electronics mainly focuses on the discovery and analysis of bifurcation, chaos, and other nonlinear behavior [810]. Research shows that the nonlinear behavior of a boost converter is controlled via digital current mode based on simulation and experimental results. The stability of a converter was analyzed by Amit Kumar Singha et al. [11]. The bifurcation phenomenon of a buck converter under current mode control was discussed, and experimental verification was performed by Biswarup Basak [12]. The chaotic bifurcation behavior of a flyback converter with peak current mode control was introduced, and the influences of different bifurcation parameters on the chaotic phenomenon were analyzed via an iterative mapping model [13].
To date, the research points for highfrequency Zsource converters [14, 15] have mainly focused on performance improvement, topology derivation and practical engineering applications [16]. The power factor correction of a Zsource converter is introduced and then it is applied to an electric vehicle battery charging system, which increased the stability of the system. A novel circuit topology and control strategy for a voltage source inverter based on a quasiZsource inverter was proposed by Hu Ruizhe [17]. The stability analysis of a system, particularly the introduction of nonlinear behavior, is currently extremely rare. The current study starts from the DC link of an ultrahigh frequency Zsource converter and adopts peak current control mode. A discrete iterative mapping model for continuous current mode is then established based on the equation of state. The bifurcation diagram of the system shows that period doubling bifurcation and the effect of reference current size on the stability of the system are determined via the characteristic value of the Jacobian matrix. The occurrence of a nonlinear phenomenon is confirmed via circuit simulation. Finally, the accuracy of the theoretical analysis is verified using the experimental data.
2. Working principle of and model for ultrahigh frequency Zsource converter
2.1. Working principle of ultrahigh frequency Zsource converter
The main structure of an ultrahigh frequency Zsource converter comprises a diode D and an impedance network that is connected between the DC voltage source and the conventional voltage source converter. The converter impedance network contains two identical inductors and two identical capacitors, which are arranged to form an Xtype structure. Fig. 1 illustrates the circuit diagram of the Zsource converter under peak current mode control. This system mainly involves a clock signal that controls the turning on of the switch. This clock signal also sets the RS flipflop to 1 at regular intervals. The switch is turn off at $Q=$ 0, and the inductor current ${i}_{L}$ increases until the required ${I}_{ref}$is reached. Afterward, the inductor inverts the output signal at $Q=$ 1. Peak current mode control exhibits good stability and improved noise elimination. It does not require harmonic compensation, and is simple and convenient to achieve. Moreover, this control mode can limit peak current in the circuit, thereby protecting the device. Consequently, a wide range of applications are obtained. Peak current mode control is the most widely used current mode control method.
Fig. 1. Schematic of an ultrahigh frequency Zsource converter based on peak current mode control
2.2. Dynamic model for ultrahigh frequency Zsource converter
The operation principle of an ultrahigh frequency Zsource converter is based on peak current control mode according to the working state of straight switch $Q$ and diode $D$. In continuous current mode, two types of working conditions can be achieved, and the circuit is switched periodically between the two modes of operation, as shown in Fig. 2.
Fig. 2. DClink equivalent circuit of the ultrahigh frequency Zsource converter
a) Equivalent circuit under shootthrough mode
b) Equivalent circuit under nonshootthrough mode
In working mode 1, the shootthrough state is represented as $Q$ on and $D$ off. The state equation is written as follows:
In working mode 2, the nonshootthrough state is represented as $Q$ off and $D$ on. The state equation is expressed as follows:
We assume that $L={L}_{1}={L}_{2}$ is the inductance of the Zsource network, $C={C}_{1}={C}_{2}$ is the capacitance of the Zsource network, ${i}_{L}$ is the inductor current of the Zsource network, ${V}_{c}$ is the capacitance voltage of the Zsource network, $r$ is the parasitic resistor of the inductor, ${R}_{1}$ is the series resistance of capacitance, $R$ is the load resistance, and ${V}_{in}$ is the output voltage.
We calculate the discrete iterative model of the system using the stroboscopic mapping method based on Eqs. (1) and (2). ${d}_{n}$ is the duty cycle of the nth period $T$, ${t}_{n}=nT$, ${x}_{n}=x\left(nT\right)$, and the discrete iterative equations can be expressed as ${x}_{n+1}=f({x}_{n},{d}_{n})$. The state equation derived from Eq. (1) and Eq. (2) is specified as Eq. (3) and Eq. (4), respectively:
where the state vector $\dot{x}$ is defined as:
${B}_{1}=0,{B}_{2}=\left[\begin{array}{c}1/L\\ \frac{1}{C}/R\end{array}\right].$
For the discrete model in the stroboscopic map, the equation is expressed as follows:
The equation of state of the system is Eqs. (3) and (4), whereas the discrete model for the system in the $n$th cycle can be obtained as:
$nT+{t}_{n}\le t\le nT+{d}_{n}T,$
$={\mathrm{}\mathrm{\varnothing}}_{2}\left({\overline{d}}_{n}xT\right)x\left({t}_{n}+{d}_{n}T\right)+{\int}_{0}^{\overline{{d}_{n}}T}{\mathrm{\varnothing}}_{2}(\overline{{d}_{n}}T\tau ){B}_{2}{V}_{in}{d}_{\tau},nT+{d}_{n}T\le t\left(n+1\right)T,$
where ${\mathrm{\varnothing}}_{1}\left({d}_{n}T\right)={e}^{{A}_{1}{d}_{n}T}$, ${\mathrm{\varnothing}}_{2}\left({d}_{n}T\right)={e}^{{A}_{2}\overline{{d}_{n}}T}$ and $\overline{{d}_{n}}=1{d}_{n}$.
When cycle $T$ is smaller, the method of approximate discretization [18] is used in this study. As a result the integral terms of these equations can be simplified and expressed as follows:
Eq. (8) can be substituted into Eq. (9) and expressed as discrete mapping Eq. (10) as follows:
The switching function can be derived as follows:
$K=[\mathrm{1,0}$], $\sigma \left({x}_{n},{d}_{n}\right)=0$ the state of the converter is altered.
3. Parameter design of ultrahigh frequency Zsource network
An ultrahigh frequency Zsource converter has certain properties that are not found in traditional converters because of the added unique Zsource impedance network, and thus, the parameter design of an ultrahigh frequency Zsource converter is particularly important. The design is related to the performance of the entire system. It also has a critical effect on our subsequent analysis.
Combined with the system requirements, the parameters of the system are listed in Table 1.
Table 1. System parameters
Switching cycle

$T$

1 µs

Through cycle

${T}_{d}$

0.4 µs

Capacitance voltage

${V}_{C}$

240 V

Duty ratio

${d}_{n}$

0.4

Inductor current

${i}_{L}$

1 A

Load resistance

$R$

20 Ω

3.1. Design of network capacitor of converter
The quality of the capacitor voltage of an ultrahigh frequency Zsource converter directly affects the quality of the voltage of the input DC link of the converter, which consequently determines the quality of the output voltage. The higher the Zsource capacitance value, the higher the system stability will be. However, the cost of the capacitor will be increased from the design point of view. To comprehensively consider various factors and to satisfy the requirements of analysis, the ultrahigh frequency Zsource converter network parameters of the capacitor value are determined in this study.
When the system works under a nonstraight state, the ultrahigh frequency Zsource capacitor is charged. The capacitance voltage value at this point is gradually increased. The current value of the capacitance of the Zsource converter is:
When the system works under a straight state, the ultrahigh frequency Zsource capacitor discharge is inductive charging, and the current on the capacitor is the same as the inductor current. The Zsource capacitance current at this point is:
The research object in this study is the ultrahigh frequency Zsource converter, and thus, switching frequency is sufficiently high. The value of the inductor current can be approximated as a constant value as follows:
Fig. 3. Ultrahigh frequency Zsource capacitance voltage waveform
On the basis of the opening and closing of the switch tube, the ultrahigh frequency Zsource capacitor voltage waveform can be obtained from Fig. 3. When Eqs. (13, 14) are combined, then this waveform can also be obtained from Fig. 3:
From the data, $\u2206{V}_{c}$ should be less than 3 % ${V}_{c}$, where ${i}_{L}={i}_{L1}={i}_{L2}$, ${V}_{c}={V}_{c1}={V}_{c2}$. The equivalent series resistance of the inductance and capacitance of the Zsource network are disregarded, then can be deduced from state space averaging equation [19]:
From Eqs. (13) to (16), the following equation can be obtained:
The aforementioned parameters are integrated into Eq. (17):
3.2. Design of inductor in converter network
The inductance value of the ultrahigh frequency Zsource network is as important as the capacitance value. The design of the inductor also affects the working status of the system. The ripple of the inductor current is related to the inductance value. The higher the inductance value, the smaller the ripple of the inductor, and the more stable the system will be. However, an increase in volume is followed by an increase in cost. Therefore, the design should comprehensively consider various factors. The inductance value is designed to fulfill the requirements of the system based on the analysis of the ripple.
The Zsource inductance voltage is a switching pulse under a steady state condition. The inductor is charged, and the inductor current increases under shootthrough state. The inductor voltage is ${V}_{c}$ during this period. The inductor is discharged, and the inductor current is reduced under nonshootthrough state. The inductor voltage is ${V}_{in}{V}_{c}$, as shown in Fig. 4.
Fig. 4. Ultrahigh frequency Zsource inductor current and voltage waveform
In a switching cycle, when $0\le t\le {d}_{n}T$, the circuit is shown in Fig. 2(a):
where ${V}_{L1}$ is the ultrahigh frequency Zsource inductor voltage under through state, and $\u2206{i}_{1}$ is the ultrahigh frequency Zsource inductor current increment under through state.
When ${d}_{n}T\le t\le T$, the circuit is shown in Fig. 2(b):
where ${V}_{L2}$ is the inductive voltage of the ultrahigh frequency Zsource converter under nonstraight through state, and $\u2206{i}_{2}$ is the inductance current increment of the ultrahigh frequency Zsource converter under nonstraight through state.
The steady state is known, and thus, the following can be obtained in a switching cycle:
Eqs. (18) to (20) can be expressed as:
Then, the following can be obtained:
The maximum allowable value of the amplitude of the harmonic current is $\u2206{i}_{L\mathrm{m}\mathrm{a}\mathrm{x}}$. The inductance value of the ultrahigh frequency Zsource converter is satisfied as follows:
In addition to the aforementioned requirements, the resonant frequency of the capacitor in the case of nonresonance is:
If the design requirement of the ultrahigh frequency Zsource network does not produce resonance, then the switching frequency of the converter must not be higher than the resonant frequency of the Zsource network in this study, i.e.:
The inductance value can be obtained as follows:
When the two preceding aspects are integrated, the value of the ultrahigh frequency Zsource converter inductor is:
From the design requirements, $\u2206{i}_{L\mathrm{m}\mathrm{a}\mathrm{x}}=8\%{i}_{L}$ is known. The circuit parameters in Table 1 are introduced into Eq. (27), which can derive:
Fig. 5. Nonlinear typical waveform of the ultrahigh frequency Zsource converter under peak current control
a) Typical waveforms of period1 state (${I}_{ref}=$ 3 A)
b) Typical waveforms of period2 state (${I}_{ref}=$ 6 A)
c) Typical waveforms of chaotic state (${I}_{ref}=$ 25 A)
4. Dynamic behavior analysis of ultrahigh frequency Zsource converter
4.1. Nonlinear phenomenon of converter
To more directly reflect the nonlinear phenomenon of the system, the simulation module of an ultrahigh frequency Zsource converter with peak current control mode is established using the state space analysis method based on MATLAB. The simulation values of the Zsource network inductor current and capacitor voltage are shown on the left of the figures.
Fig. 5 illustrates the time domain waveform of the inductor current of the ultrahigh frequency Zsource converter under different reference current conditions. Fig. 5(a) shows the reference current${I}_{ref}=$ 3 A. The figure indicates that the system works under period1 state. The simulation results on the left show that ${U}_{c}$ is the capacitance voltage and ${i}_{L}$ is the inductor current of the Zsource network. The bifurcation diagram of ${i}_{L}$ is presented on the right. Fig. 5(b) shows the reference current ${I}_{ref}=$ 6 A. The system can work under period2 state. Fig. 5(c) shows the reference current ${I}_{ref}=$ 25 A. The system is known to be under a state of chaos.
When the input voltage of the converter is set as ${V}_{in}=$ 80 V, ${L}_{1}={L}_{2}=L=$ 0.5 mH, ${C}_{1}={C}_{2}=C=$ 0.013 μf, ${R}_{1}\text{=}$ 0.5 Ω, $r=$ 0.02 Ω, $R=$ 18 Ω, $K=$–1, ${I}_{ref}=$ 230 A, and $f=$ 1 MHz. The output current reference value is selected as the analysis variable, and the bifurcation diagram is drawn as shown in Fig. 6.
Fig. 6. Inductance current bifurcation diagram with reference current Iref as the bifurcation parameter
4.2. Converter stability analysis
From the preceding discussion, the variation of the reference current parameter or the external disturbance will change the stable operation of the system, and thus, produce the bifurcation and chaos phenomena. The Jacobian matrix is an effective tool for analyzing stability. In this study, we use the Jacobian matrix to analyze the stability of the fixed point of the converter and the characteristics of the local bifurcation. The Jacobian matrix of the fixed point is established in the beginning.
We assume that the controlled system is stable under a single period state, and that the input voltage and reference voltage always remain unchanged. ${x}_{n}=\widehat{x}+{X}_{Q}$, ${d}_{n}=\widehat{d}+D$, ${X}_{Q}$ and $D$ are set as the periodic solutions for a steady state. The perturbation and linearization [20, 21] of Eq. (5) can then be expressed as follows:
At $\sigma \left({x}_{n},{d}_{n}\right)=0$, the following can be obtained:
Consequently, the following can be obtained:
Eq. (30) can be substituted into Eq. (28) to yield Eq. (31):
We can obtain the Jacobian matrix as follows:
where:
$\frac{\partial \sigma}{\partial {x}_{n}}=K{e}^{{A}_{1}{d}_{n}T},\frac{\partial \sigma}{\partial {d}_{n}}=KT{e}^{{A}_{1}{d}_{n}T}{A}_{1}{x}_{n}+KT{B}_{1}{V}_{in},\frac{\partial f}{\partial {x}_{n}}={e}^{{A}_{2}\left(1{d}_{n}\right)T}{e}^{{A}_{1}{d}_{n}T},$
$\frac{\partial f}{\partial {d}_{n}}={A}_{2}T{e}^{{A}_{2}\left(1{d}_{n}\right)T}.{e}^{{A}_{1}{d}_{n}T}{x}_{n}+{e}^{{A}_{2}\left(1{d}_{n}\right)T}{A}_{1}T{e}^{{A}_{1}{d}_{n}T}{x}_{n}$
${A}_{2}T{e}^{{A}_{2}\left(1{d}_{n}\right)T}{B}_{1}{V}_{in}{d}_{n}T+T{e}^{{A}_{2}\left(1{d}_{n}\right)T}{B}_{1}{V}_{in}T{e}^{{A}_{2}\left(1{d}_{n}\right)T}{B}_{2}{V}_{in}.$
Before the eigenvalues of the Jacobian matrix of the system is calculated, the steady state periodic solutions ${X}_{Q}$ and $D$ of the discrete mapping equations of the controlled ultrahigh frequency Zsource converter system are first determined. The equilibrium point of the discrete mapping equation of the system is the single period steady state solution for the system.
Let ${x}_{n+1}={x}_{n}={X}_{Q}$,$x\left(nT+{d}_{n}T\right)={X}_{D}$ and ${d}_{n}=D$. Through Eqs. (8) and (9), the following can be obtained:
Eqs. (33) and (34) are then derived as:
Simultaneously, the switching function satisfies:
The schematic of the peak current control of the ultrahigh frequency Zsource converter is shown in Fig. 1. On the basis of the aforementioned parameters, the characteristic value of the Jacobian matrix is calculated with reference current ${I}_{ref}$ as the bifurcation parameter. When ${I}_{ref}=$ 3.5 A, the steady state periodic solution is obtained via numerical calculation:
The system is stable given that $\left{\lambda}_{1}\right<$ 1 and $\left{\lambda}_{2}\right<$ 1 at reference current ${i}_{ref}=$ 3.5 A. When $\left{\lambda}_{\mathrm{m}\mathrm{a}\mathrm{x}}\right=\mathrm{m}\mathrm{a}\mathrm{x}\{\left{\lambda}_{1}\right,\left{\lambda}_{2}\right\}$, the system is under a single period steady state. As shown in Fig. 7, all the characteristic values of the Jacobian matrix of the ultrahigh frequency Zsource converter lie on the real axis of the coordinate axes and the change of $\left{\lambda}_{1}\right$ is faster than that of $\left{\lambda}_{2}\right$. The change of ${\lambda}_{2}$ is extremely slow. The system becomes unstable as long as a characteristic value exists over the unit circle. The maximum $\left{\lambda}_{1}\right$ is selected as the basis to study the stability of the system. When the value of ${i}_{ref}$ is between 4.8 and 4.9, $\left{\lambda}_{1}\right$ will be larger than 1. Then, the system will enter an unstable state from a stable operation.
Fig. 7. Motion change trend of the Jacobian matrix eigenvalue
To determine the critical value of ${i}_{ref}$, the variations of the eigenvalues of the Jacobian matrix are listed when ${i}_{ref}=$ 45 A in Table 2.
Table 2. Eigenvalues of the different values of the reference current Iref for peak current mode control
Iref

$D$

${\lambda}_{1}$

${\lambda}_{2}$

System state

4.5

0.6294

0.2161

−0.4071

Stable

4.6

0.6245

0.2220

−0.3801

Stable

4.7

0.6196

0.2282

0.3546

Stable

4.8

0.6148

0.2349

−0.3306

Stable

4.9

0.1058

1.3586

0.0004

Bifurcation

5.0

0.1130

1.4873

0.0005

Unstable

As shown in Table 2, when ${I}_{ref}\approx $ 4.9 A, the value of $\left{\lambda}_{1}\right$ is close to 1. ${I}_{ref}=$ 4.862 A, ${\lambda}_{1}=$ –1.2241 and ${\lambda}_{2}=$ –0.0004 can be calculated through a large number of numerical calculations. The value of ${I}_{ref}$ at this time is the critical value of system instability. If the value of ${I}_{ref}$ exceeds this value, then the system will enter bifurcation. When the value of ${I}_{ref}$ is less than 4.862 A, then the eigenvalues of the Jacobian matrix of the system at fixed points are less than 1. The fixed point is a stable node at this instance. When the value of ${I}_{ref}$ is higher than 4.862 A, the system is exposed to period doubling bifurcation. The original fixed point of the system of period 1 is unstable at this instance. Instead, two stable solutions are available for period 2. The situation is illustrated in Fig. 6.
The Jacobian matrix method is used to judge stability. This method can be applied to accurately analyze and identify the location of the bifurcation point. The bifurcation point is determined using this method in practical applications, and then the parameters of the converter are designed. Finally, to ensure that the system will work in a stable running area, the influence of the circuit parameters on the stability of the fixed point and the system are discussed as follows. The different values of reference current ${I}_{ref}$ are selected as the bases in this study. The effects of the inductance $L$ and capacitance $C$ of the Zsource network on system stability is analyzed. The corresponding fixed point stability boundary curves are illustrated in Fig. 8. From Fig. 8(a), a conclusion can be drawn that the area below the curve is unstable. With the increase in the reference current ${I}_{ref}$, the unstable region of the fixed point of capacitor $C$ will continue to increase. As shown in Fig. 8(b), the region below the curve is stable. With the increase in the reference current ${I}_{ref}$, the stability region of the fixed point of inductance L becomes smaller. Fig. 8(c) illustrates the stability of the three parameter domains using the Jacobian matrix method.
Fig. 8. Stability region boundary curves under different parameter variations
a) Influence of inductance parameters on the stability region
b) Influence of capacitor parameters on the stability region
c) Distribution map of the stable region of the three parameters of the Jacobian matrix method
5. Experiment verification
To verify the accuracy of the theoretical analysis and the simulation of the converter circuit, a relevant circuit verification analysis is conducted. The circuit model of the ultrahigh frequency Zsource DC/DC converter based on peak current control mode is built based on the aforementioned parameters. The experimental circuit is consistent with the simulation model. A KLP250 isolation drive chip is applied in the drive circuit. The parameters of the given circuit are as follows: input voltage ${V}_{in}=$ 80 V, $f=$ 1 MHz, load resistance $R=$ 18 Ω, capacitance resistance ${R}_{1}=$ 0.5 Ω, inductance resistance $r=$ 0.02 Ω, ultrahigh frequency Zsource network inductance ${L}_{1}={L}_{2}=L=$ 0.5 mH and network capacitance ${C}_{1}={C}_{2}=C=$ 0.013 μf.
The reference current ${I}_{ref}$ changes from 2 A to 20 A under the driving signal of the switch tube and the clock signal in the cycle. The experimental waveforms of the inductor current and the capacitor voltage of the Zsource network are shown in Fig. 9. Channels one and two show the value of the inductor current and the capacitor voltage under period 1, period 2, and chaotic states. Fig. 9(a) shows a stable waveform under period1 state at reference current ${I}_{ref}=$ 3 A. Fig. 9(b) shows the waveform under period2 state at reference current ${I}_{ref}=$ 6 A. Fig. 9(c) shows that the system enter a chaotic state at reference current ${I}_{ref}=$ 25 A.
Fig. 9. Experimental waveforms of the inductor current and capacitor voltage under different reference currents
a)${I}_{ref}=$3 A (Typical waveforms under period1 state)
b)${I}_{ref}=$ 6 A (Typical waveforms under period2 state)
c)${I}_{ref}=$ 25 A (Typical waveforms under a chaotic state)
The experimental results indicate that the experimental waveforms are in full compliance with the simulation model results of the circuit at the critical point of the reference current. The bifurcation diagram is consistent with the model based on the discrete iterative map equation model. The accuracy of the theoretical analysis is verified. In summary, the ultrahigh frequency DC/DC Zsource converter under different reference currents will exhibit a nonlinear behavior.
6. Conclusions
In view of the nonlinear characteristics of power electronic converters in application processes, the nonlinear dynamic behavior of an ultrahigh frequency Z source converter under peak current control is investigated in this study. A discrete iterative mapping model is established based on the equation of state of the converter for the analysis and drawing of the bifurcation diagram of the Zsource converter when different parameters are given. The stability of the converter is analyzed using the trajectory of the eigenvalues of the Jacobian matrix. Moreover, the stable operating region is determined based on the parameters of the Zsource inductance, capacitance, and reference current at an ultrahigh frequency. The accuracy of the theoretical analysis is verified via the experimental results. The findings of this study can provide references for analyzing the nonlinear mechanism of this type of converter. Moreover, this study provides important theoretical guidance for the optimal design and control of converter parameters.
Acknowledgements
This study is supported by the National Natural Science Foundation of China (Grant No. 51607020) and Chongqing Municipal Science and Technology Commission of Basic Science and CuttingEdge Technology Research Projects funded by the General (Grant No. cstc2016jcyjA0324, cstc2015jcyjA70013).
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